the magnitude of “clicks and pops”. Increasing the value of

C

presents a tradeoff: as the size of C

time increases. There is a linear relationship between the

size of C

turn-on times for various values of C

C

B

T

ON

0.1µF

80ms

0.22µF

170ms

0.33µF

270ms

0.47µF

370ms

0.68µF

490ms

1.0µF

920ms

2.2µF

1.8sec

3.3µF

2.8sec

4.7µF

3.4sec

10µF

7.7sec

In order eliminate “clicks and pops”, all capacitors must be

discharged before turn-on. Rapidly switching V

allow the capacitors to fully discharge, which may cause

“clicks and pops”. In a single-ended configuration, the output

is coupled to the load by C

high value. C

Ω resistors.

Depending on the size of C

can be relatively large. To reduce transients in single-ended

mode, an external 1k

Ω–5kΩ resistor can be placed in par-

allel with the internal 20k

Ω resistor. The tradeoff for using

this resistor is increased quiescent current.

AUDIO POWER AMPLIFIER DESIGN

Design a Dual 70mW/32

Ω Audio Amplifier

Given:

Power Output

70 mW

Load Impedance

32

Ω

Input Level

1 Vrms (max)

Input Impedance

20k

Ω

Bandwidth

The design begins by specifying the minimum supply voltage

necessary to obtain the specified output power. One way to

find the minimum supply voltage is to use the Output Power

vs Supply Voltage curve in the Typical Performance Char-

acteristics section. Another way, using Equation (5), is to

calculate the peak output voltage necessary to achieve the

desired output power for a given load impedance. To ac-

count for the amplifier’s dropout voltage, two additional volt-

ages, based on the Dropout Voltage vs Supply Voltage in the

Typical Performance Characteristics curves, must be

added to the result obtained by Equation (5). For a

single-ended application, the result is Equation (6).

(5)

V

DD

≥ (2V

(6)

The Output Power vs Supply Voltage graph for a 32

Ω load

indicates a minimum supply voltage of 4.8V. This is easily

met by the commonly used 5V supply voltage. The additional

voltage creates the benefit of headroom, allowing the

LM4810 to produce peak output power in excess of 70mW

without clipping or other audible distortion. The choice of

supply voltage must also not create a situation that violates

maximum power dissipation as explained above in the

Power Dissipation section. Remember that the maximum

power dissipation point from Equation (1) must be multiplied

by two since there are two independent amplifiers inside the

package. Once the power dissipation equations have been

addressed, the required gain can be determined from Equa-

tion (7).

(7)

Thus, a minimum gain of 1.497 allows the LM4810 to reach

full output swing and maintain low noise and THD+N perfro-

mance. For this example, let A

The amplifiers overall gain is set using the input (R

feedback (R

set at 20k

Ω, the feedback resistor is found using Equation

(8).

A

(8)

The value of R

Ω.

The last step in this design is setting the amplifier’s −3db

band magnitude variation limit, the low frequency response

must extend to at lease one−fifth the lower bandwidth limit

and the high frequency response must extend to at least five

times the upper bandwidth limit. The gain variation for both

limit. The results are an

f

(9)

and a

f

*

5 = 100kHz

(10)

As stated in the External Components section, both R

conjunction with C

pass filters. Thus to obtain the desired low frequency re-

into consideration. The combination of two single order filters

at the same frequency forms a second order response. This

results in a signal which is down 0.34dB at five times away

from the single order filter −3dB point. Thus, a frequency of

20Hz is used in the following equations to ensure that the

response is better than 0.5dB down at 100Hz.

C

i

≥ 1/(2π * 20kΩ * 20Hz) = 0.397µF; use 0.39µF.(11)

C

o

≥ 1/(2π *32Ω * 20Hz) = 249µF; use 330µF. (12)

The high frequency pole is determined by the product of the

desired high frequency pole, f

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